Voltage regulators with load-dependent bias

ABSTRACT

This document describes systems and techniques related to voltage regulators. The subject matter of this document can be embodied in a method that includes measuring an output current of a switching regulator. The switching regulator includes a high-side transistor and a low side-transistor wherein the high-side transistor and the low-side transistor are driven using a first gate voltage and a second, different gate voltage, respectively. The method also includes adjusting a direct-current (DC) voltage source of the switching regulator such that the first gate voltage is adjusted in accordance with the measured output current.

TECHNICAL FIELD

The following disclosure relates to semiconductor voltage regulatordevices.

BACKGROUND

Voltage regulators, such as DC to DC converters, are used to providestable voltage sources for electronic systems. Efficient DC to DCconverters are particularly needed for battery management in low powerdevices, such as laptop notebooks and cellular phones. Switching voltageregulators (or simply “switching regulators”) are known to be efficientDC to DC converters. A switching regulator generates an output voltageby converting an input DC voltage into a high frequency voltage, andfiltering the high frequency input voltage to generate the output DCvoltage. Specifically, the switching regulator includes a switch foralternately coupling and decoupling an input DC voltage source, such asa battery, to a load, such as an integrated circuit. An output filter,typically including an inductor and a capacitor, is coupled between theinput voltage source and the load to filter the output of the switch andthus provide the output DC voltage. A controller, such as a pulse widthmodulator or a pulse frequency modulator, controls the switch tomaintain a substantially constant output DC voltage.

SUMMARY

In general, in one aspect this disclosure features a method thatincludes measuring an output current of a switching regulator. Theswitching regulator includes a high-side transistor and a lowside-transistor wherein the high-side transistor and the low-sidetransistor are driven using a first gate voltage and a second, differentgate voltage, respectively. The method also includes adjusting adirect-current (DC) voltage source of the switching regulator such thatthe first gate voltage is adjusted in accordance with the measuredoutput current.

In another aspect the disclosure features a switching regulator havingan input terminal and an output terminal. The switching regulatorincludes a high-side transistor between the input terminal and anintermediate terminal, a low-side transistor between the intermediateterminal and ground, and a controller that drives the high-side andlow-side transistors to alternately couple the intermediate terminal tothe input terminal and ground. The controller drives the high-sidetransistor with a first gate voltage and the low-side transistor with asecond, different, gate voltage, and is configured to adjust adirect-current (DC) voltage source of the switching regulator such thatthe first gate voltage is adjusted in accordance with a current measuredat the output terminal.

In another aspect, the disclosure features a system that includes acurrent sensor configured to measure an output current at an outputterminal of a switching regulator. The switching regulator includes ahigh-side transistor driven by a first gate voltage, and a lowside-transistor driven by a second gate voltage. The system alsoincludes a feedback circuit connected to a direct-current (DC) voltagesource of the switching regulator. The feedback circuit is configured toadjust the DC voltage source such that the first gate voltage isadjusted in accordance with the measured output current.

Implementations can include one or more of the following.

The DC voltage source can be adjusted such that a higher output currentresults in a higher first gate voltage. The first gate voltage isbetween 1.7V and 1.8V for substantially no output current. The DCvoltage source can be adjusted such that the first gate voltage is atleast 2V for a 30 A output current. The DC voltage source can beadjusted such that the first gate voltage is a monotonic function of theoutput current for a range of output current values. The DC voltagesource can be adjusted such that a saturation current of the high-sidetransistor is substantially constant for a range of output currentvalues.

The switching regulator can include a high-side driver circuit betweenthe controller and the high-side transistor. The controller can drivethe high-side transistor by providing a control signal to the high-sidedriver circuit. The high-side driver circuit can be coupled to the DCvoltage source through a switch, such that an open configuration of theswitch allows for maintaining a drive voltage sufficient to maintain asubstantially constant saturation current for the high-side transistor.The high-side driver circuit can include an inverter with an inputterminal, an output terminal, a positive voltage terminal and a negativevoltage terminal. The input terminal can be connected to the controllerand the output terminal can be connected to the gate of the high-sidetransistor. The controller can be configured to receive a signalindicative of a measurement of the output current. A higher outputcurrent can result in a higher first gate voltage. The first gatevoltage can be between 1.7V and 1.8V for substantially no outputcurrent. The first gate voltage can be at least 2V for an output currentsubstantially equal to 30 A. The first gate voltage can be a monotonicfunction of the output current for a range of output current values. Anoutput of the DC voltage can be adjustable such that a saturationcurrent of the high-side transistor is substantially constant for arange of output current values.

The feedback circuit can be configured to receive a signal indicative ofa measurement of the output current. The feedback circuit can include acomputing device configured to determine an output voltage of the DCvoltage source based on the measurement of the output current. Thefeedback circuit can be configured to adjust the DC voltage source suchthat a higher output current results in a higher output voltage for theDC voltage source. The feedback circuit can be configured to adjust theDC voltage source such that the output voltage of the DC voltage sourceis substantially proportional to the output current for a range ofoutput current values.

Certain implementations may have one or more of the followingadvantages. By having an adjustable DC voltage source to drive a gate ofthe power transistor, efficiency of a voltage regulator can beincreased. Having an adjustable DC voltage source can help in quicklypulling up the voltage at an intermediate node of the voltage regulator,thereby reducing switching time. Adequate saturation current needed todrive the switching transition can be provided by adjusting the DCvoltage source in accordance with the output current. Adjusting thevoltage to a low value, except when needed for pulling up theintermediate terminal, can increase the life expectancy of oxide layersof the voltage regulator, and hence that of the integrated circuithousing the voltage regulator.

Providing a switch to prevent a discharge (often referred to as akickback discharge) from the low-side drive circuit can reduce switchingtime by maintaining an adequate pull down strength of the low-side drivecircuit. A transistor-based switch provided within the integratedcircuit can obviate the need for an external resistor (to prevent thedischarge) which in turn increases the charging time. The transistorbased switch can provide discharge protection without introducing avoltage drop associated with using a simple diode.

Connecting the low-side driver circuit to a DC voltage source (ratherthan the ground) can also provide discharge protection, while increasingefficiency of the regulator by having a reduced voltage swing. Thereduced swing in turn can achieve power savings. Connecting the low-sidedriver circuit to a DC voltage source can also provide more options to adevice designer. For example, the threshold voltage of the high-sidedevice can be lowered to a value such that an effective thresholdvoltage of the high-side device is substantially same as or at leastcomparable to the threshold voltage of the low-side device. This in turncan increase efficiency by reducing diode reverse recovery lossesassociated with the regulator. By making the DC voltage sourceadjustable, the integrated circuit can be made adaptive to a range ofground bounce (elevation of the internal ground of the integratedcircuit with respect to the actual ground, due to, for example, thepresence of parasitic inductances) associated with the integratedcircuit.

The details of one or more implementations are set forth in theaccompanying drawings and the description below. Other features,aspects, and advantages will become apparent from the description, thedrawings, and the claims.

DESCRIPTION OF DRAWINGS

Exemplary implementations will hereinafter be described in conjunctionwith the appended drawings, wherein like designations denote likeelements, and wherein:

FIG. 1 is a circuit diagram of a switching regulator.

FIG. 2 is a circuit diagram of a switching regulator where a DC voltagesource is adjusted in accordance with an output current.

FIG. 3 is a circuit diagram of a switching regulator with low-sidedischarge protection.

FIG. 4 is a circuit diagram of a switching regulator with low-sidedischarge protection.

FIG. 5 is a flowchart showing an example sequence of operations foradjusting a DC voltage source in accordance with an output current.

DETAILED DESCRIPTION

Power electronics and systems are in a continuous push to continue toimprove overall performance. Performance can be measured, for example,by power dissipation, electrical robustness/reliability, and cost. Thesemetrics can be affected, for example, by the device architecturechoices, circuit architecture choices. For example, the demand for lowerpower dissipation and switching loss has resulted in lower gate drivevoltage levels while maintaining or improving drive current.

Referring to FIG. 1, a switching regulator 10 is coupled to a first highdirect current (DC) input voltage source 12, such as a battery, by aninput terminal 20. The voltage at the input terminal 20 can be referredto as V_(DDH). The switching regulator 10 is also coupled to a load 14,such as an integrated circuit, by an output terminal 24. The switchingregulator 10 serves as a DC-to-DC converter between the input terminal20 and the output terminal 24. The switching regulator 10 includes aswitching circuit 16 which serves as a power switch for alternatelycoupling and decoupling the input terminal 20 to an intermediateterminal 22. The switching circuit 16 includes a rectifier, such as aswitch or diode, coupling the intermediate terminal 22 to ground.Specifically, the switching circuit 16 can include a first transistor40, called a high-side transistor, having a source connected to theinput terminal 20 and a drain connected to the intermediate terminal 22and a second transistor 42, called a low-side transistor, or synchronoustransistor, having a drain connected to ground and a source connected tothe intermediate terminal 22.

In one implementation, the first transistor 40 can be a Positive-ChannelMetal Oxide Semiconductor (PMOS) transistor, and the second transistor42 can be a Negative-Channel Metal Oxide Semiconductor (NMOS)transistor. In another implementation, the first transistor 40 and thesecond transistor 42 can both be NMOS transistors. In anotherimplementation, the first transistor 40 can be a PMOS, NMOS, or aLateral Double-diffused Metal Oxide Semiconductor (LDMOS), and thesecond transistor 42 can be an LDMOS.

The intermediate terminal 22 is coupled to the output terminal 24 by anoutput filter 26. The output filter 26 converts the rectangular waveformof the intermediate voltage at the intermediate terminal 22 into asubstantially DC output voltage at the output terminal 24. Specifically,in a buck-converter topology, the output filter 26 includes an inductor44 connected between the intermediate terminal 22 and the outputterminal 24 and a capacitor 46 connected in parallel with the load 14.During a high-side conduction period, the first transistor (alsoreferred to as the high-side transistor) 40 is closed (or switched on),and the DC input voltage source 12 supplies energy to the load 14 andthe inductor 44 via the first transistor 40. On the other hand, during alow-side conduction period, the second transistor (also referred to asthe low side transistor) 42 is closed, and current flows through thesecond transistor 42 as energy is supplied by the inductor 44. Theresulting output voltage V_(OUT) is a substantially DC voltage.

The switching regulator also includes a controller 18, a high-sidedriver (also referred to as a high-side driver circuit) 80 and alow-side driver (also referred to as a low-side driver circuit) 82 forcontrolling the operation of the switching circuit 16. A first controlline 30 connects the high-side transistor 40 to the high-side driver 80,and a second control line 32 connects the low-side transistor 42 to thelow-side driver 82. The high-side and low-side drivers are connected tothe controller 18 by control lines 84 and 86, respectively. Thecontroller 18 causes the switching circuit 16 to alternate betweenhigh-side and low-side conduction periods so as to generate anintermediate voltage V_(X) at the intermediate terminal 22 that has arectangular waveform. The controller 18 can also include a feedbackcircuit 50, that can be configured to measure the output voltage V_(OUT)and the current I_(load) passing through the output terminal 24.Although the controller 18 is typically a pulse width modulator, themethods and systems described in this document can be also applicable toother modulation schemes, such as pulse frequency modulation.

In some implementations, the high-side transistor 40 and the high-sidedriver 80 can be collectively referred to as a high-side device. Thehigh side driver 80 can include a high-side capacitor 62 and a high-sideinverter 64. The high-side inverter 64 includes a positive voltageterminal 66 that is coupled to a capacitor 65 that is configured to holda boost voltage V_(BST) for the high-side driver. The high-side inverter64 also includes a negative voltage terminal 68 that is connected to theintermediate terminal 22 of the switching regulator 10. The high-sideinverter 64 can be connected to the controller 18 by the control line84, and to the gate of the high-side transistor 40 by the control line30. The controller 18 can be configured to control the inverter 64 toswitch on or switch off the high-side transistor 40.

In some implementations, the low-side transistor 42 and the low-sidedriver 82 can be collectively referred to as a low-side device. Thelow-side driver 82 can include a low-side capacitor 72 and a low-sideinverter 74. The low-side inverter 74 includes a positive voltageterminal 76 that is coupled to a second DC input voltage source 28. Thevoltage V_(CC) from the DC voltage source 28 can be used to supply powerto the low-side driver 82. In some implementations, the DC voltagesource 28 can be adjustable such that the output of the DC voltagesource 28 can be varied within a range. The low-side inverter 74 alsoincludes a negative voltage terminal 78 that is connected to theinternal ground terminal 79 of the switching regulator 10. The internalground 79 of the switching regulator 10 can be at a different potentialthan the actual ground because of the presence of parasitic inductancesrepresented in FIG. 1 as the inductor 83. The low-side inverter 74 canbe connected to the controller 18 by the control line 86, and to thegate of the low-side transistor 42 by the control line 32. Thecontroller 18 can be configured to control the inverter 74 to switch onor switch off the low-side transistor 42.

A voltage V_(DDH), for example 12V, is applied to the high-sidetransistor 40, and when the high-side transistor 40 is on, current flowsthrough the transistor 40 and the inductor 44. In contrast, when thelow-side transistor 42 is on, the inductor 44 pulls current from theground. Under normal operation, the regulator 10 switches betweenturning the high-side transistor 40 and the low-side transistor 42 onsuch that the output of the filter 26 produces the desired voltageV_(OUT). V_(OUT) is a voltage between 0V and V_(DDH).

To improve efficiency of the regulator, it is desirable to have thehigh-side transistor 40 on while the low-side transistor 42 is off, andvice versa. However, some deadtime may be required between the switchingin order to avoid having both transistors 40, 42 on at same time, whichcan cause shoot-through and result in significant efficiency losses anddamage to the transistors. Thus, there is a short period, the intrinsicdeadtime t_(d), between each high-side conduction and low-sideconduction period in which both transistors are open.

When both transistors 40, 42 are off, current through the inductor 44will not instantly drop to zero. The voltage across the inductor isdetermined by Equation 1:V=L(di/dt),  (Equation 1)where V is the voltage, L is the inductance, and i is the current in theinductor. As the inductor current decreases, the voltage at the inputend, i.e. near V_(DDH), of the inductor is forced to be negative. Whenthis voltage reaches a value (e.g. −0.7 V) that causes the low-sidetransistor 42 to reach a corresponding threshold voltage, the low-sidetransistor 42 begins conducting current into the inductor.

The high-side transistor 40 and the low-side transistor 42 can becontrolled by controlling the gate voltage at the respective gates.Changing the gate voltage of the transistors can affect powerdissipation and/or efficiency of the regulator 10. In someimplementations, if the gate voltage is adjusted such that a voltagebetween the gate and source (V_(gs)) is increased, the increase canresult in a lower ON-resistance (or higher conductance), therebyreducing resistive losses associated with the corresponding transistor.However, in some implementations, an increased V_(gs) can result in anincreased switching loss.

In some cases, when the high-side transistor is switched on and currentflows from the DC source 12 through the high-side transistor 40 into theinductor 44, the voltage at the intermediate terminal 22 can drop to avoltage lower than the V_(gs) of the high-side transistor 40. This canlead to a drop in the value of V_(BST) due to, for example, chargesharing with the gate of the high-side transistor 40. For example, fordevices having Vgs of about 1.8V, the voltage at the intermediateterminal 22 can drop to about 0.9V during the switching, which can inturn lead to a loss in saturation current available for driving theswitching transition. This can result in a slow pull up of the voltageat the intermediate terminal 22, resulting in increased switchinglosses.

In some implementations, the switching losses can be reduced bypreventing the drop in V_(BST). This can be done, for example, byadjusting V_(CC) in accordance with an output current and providingcircuitry to ensure that Vgs is adjusted accordingly and enoughsaturation current is available for the high-side transistor 40 duringthe switching transition.

FIG. 2 shows a switching regulator 200 configured to increase efficiencyand reduce switching losses. The regulator 200 includes a transistor 90driven by an inverter 94. The inverter, and consequently the transistor90 can be controlled by the controller 18. The transistor 90 is of adifferent type than transistors 40 and 42. For example, if transistors40 and 42 are nMOS type transistors (i.e., n-channel MOSFETs), then thetransistor 90 is of pMOS type (i.e., a p-channel MOSFET). Alternatively,if the transistors 40 and 42 are of pMOS type, the transistor 90 is ofnMOS type. A source of the transistor 90 is connected to the positivevoltage terminal 66 of the high-side inverter 64, and a drain of thetransistor 90 is coupled to the DC voltage source 28. Other portions ofthe regulator 200 can be substantially identical to the regulator 10described with reference to FIG. 1.

In operation, when the high-side device is turned on, current flows fromthe DC source 12 through the high-side transistor 40 and into the load14. The feedback circuit 50 can measure the load current I_(load) andprovide a feedback signal for adjusting V_(CC) in accordance with theload current. The transistor 90 maintains an adequate drive voltage forthe high side device such that the saturation current of the high-sidetransistor 40 does not decrease with an increase in the load current.

In some implementations, the DC voltage source 28 can be regulated by adifferent controller internal or external to the regulator 200, based onthe feedback signal from the feedback circuit 50. In otherimplementations, the DC voltage source 12 can be connected to replacethe DC voltage source 28.

As the V_(CC) is increased in accordance with the load current, thetransistor 90 is switched on to maintain the drive voltage for thehigh-side transistor 40 and enough saturation current at the high-sidetransistor 40 is made available to make the switching fast andefficient. In some implementations, the overdrive in the high-sidetransistor 40 is low (e.g., 0.9V for a threshold of 0.5V), and a smallchange in V_(gs) leads to a comparatively large increase in thesaturation current.

The V_(CC) can be varied monotonically for a range of output currentvalues. For example, for a no-load condition (i.e., an output current of0 A), V_(CC) can be between 1.7V and 1.8V. For a load current of 30 A,V_(CC) can be increased to, for example, 2V, to compensate for theadditional load current. For output current values between 0 A and 30 A,V_(CC) can be monotonically varied from between 1.7V-1.8V and 2V,respectively. Within this range, V_(CC) can be, for example, a linear orquadratic function of the output current.

Referring back to FIG. 1, when the low-side transistor 42 turns off andthe high-side transistor 40 turns on, the switching can result in largevoltage transients on the intermediate terminal 22. The resulting fastrate of voltage change can produce a displacement current on the drainside of the low-side transistor 42, due to, for example, presence ofparasitic inductance represented by the inductor 83. The displacementcurrent can cause the gate voltage of the low-side transistor to risemomentarily, thereby partially turning on the low-side transistor 42. Acombination of the above effects causes the internal ground 79 of theregulator to be pulled up to a level higher than the external ground.This is often referred to as a ground bounce, and causes the capacitor72 to discharge through the inductor 43 into the off-chip bypasscapacitor 47. Due to this discharge of the capacitor 72, the pull-downstrength (also referred to as the drive) of the low-side transistor 42is reduced. A combination of the weaker pull-down strength and the gatevoltage induced by the displacement current can result in switchinglosses often referred to as kickback. In some implementations, thekickback can be reduced by placing a sufficiently high valued resistorin the discharge path, for example, between the inductor 43 and thecapacitor 47. While such a resistor can be effective in reducing thekickback, the resistor can also undesirably increase a charge-up time(also referred to as a rise time) for the capacitor 72.

In some implementations, the kickback can be reduced by providing adischarge protection switch within the regulator. An example of such aregulator 300 is shown in FIG. 3. The regulator 300 includes an internalswitch 108 that prevents the capacitor 72 from discharging into thecapacitor 47 possibly through the parasitic inductor 43. In someimplementations, the switch 108 includes a transistor 106 and aninverter 104. The transistor 106 is of a different type than thetransistors 40 and 42. For example, if transistors 40 and 42 are nMOStype transistors, then the transistor 106 is of pMOS type.Alternatively, if the transistors 40 and 42 are of pMOS type, thetransistor 106 is of nMOS type. In some implementations, the transistor106 can be referred to as an isolation transistor. A drain of thetransistor 106 is connected to the external capacitor 47 and thepositive terminal of the DC voltage source 28, possibly through theparasitic inductor 43. The source of the transistor 106 is coupled tothe positive voltage terminal 76 of the low-side inverter 74. The gateof the transistor 106 is connected to the inverter 104 that controls thetransistor 106 based on control signals received from the controller 18.The positive voltage terminal 105 of inverter 104 is connected to thesource of the transistor 106, and the negative voltage terminal 103 ofthe inverter 104 is connected to the internal ground 79.

In operation, when the internal ground 79 is pulled up to a level higherthan the actual ground, and a kickback condition is created, thecontroller 18 can be configured to switch off the transistor 106 therebyopening the switch 108. This opens the connection between the capacitor72 and the external bypass capacitor 47, thereby preventing a dischargefrom the capacitor 72. The capacitor 72 can therefore retain the chargenecessary for providing adequate pull-up strength for the low-sidetransistor 42, thereby reducing the switching losses resulting from thekickback effect. By using a transistor based switch 108 rather than adiode, undesirable diode drops in the charging path of the capacitor 72can be avoided.

FIG. 4 shows another example configuration for reducing kickback relatedlosses in a switching regulator. In this example, the regulator 400includes a low-side driver 482 where the negative voltage terminal 78 ofthe low-side inverter 74 is connected to the DC voltage source 28(rather than the internal ground 79). The positive voltage terminal 76of the low-side inverter 74 is connected to the input terminal 20 suchthat the low-side inverter is powered on the positive voltage side bythe DC voltage source 12. In some implementations, the capacitor 72 isconnected between the internal ground and a source of the transistor 90.The output of the DC voltage sources 12 and 28 are kept at differentlevels. For example, the output V_(DDH) of the DC voltage source 12 canbe kept at 12V and the output V_(CC) of the DC voltage source 28 can bekept at a lower value such as 1.8V.

The regulator 400 depicted in FIG. 4 can provide several advantages. Forexample, undesirable kickback related effects can be reduced by blockinga discharge of the capacitor 72 using the transistor 90. When thelow-side device is turned off, the controller 18 can be configured toopen the transistor 90 such that the capacitor 72 does not discharge to,for example, the capacitor 65.

Using a non-zero V_(CC) as a ground reference reduces the voltagedifference between the positive and negative voltage terminals (76 and78, respectively), and can lead to significant savings in powerconsumption. For example, if the V_(DDH) is at 12V, and the V_(CC) is at1.8V, the difference between the terminals is 10.2V (rather than 12V forthe case when the negative voltage terminal 78 is connected to ground),and a power saving proportional to a square of the ratio between 12 and10.2 can be achieved. Such reduced gate voltage swing also reducescapacitive losses. Further, using the non-zero V_(CC) bias in the OFFstate of the low-side transistor 42 enables easier turn-on of thetransistor 42 in the third quadrant of operation.

Using a non-zero V_(CC) allows for increased flexibility in designingthe regulator 400. Various levels of V_(CC) can be used as long asV_(CC) does not exceed the threshold voltage V_(T) of the low-sidetransistor 42. For example, for V_(T) of about 4V, VCC can be kept at1.8V such that the effective threshold voltage V_(Teff) is about 2.2Vfor the low-side transistor 42.

In some implementations, it can be desirable to have comparablethreshold voltages for the high-side transistor 40 and the low-sidetransistor 42. While design limits prevent the threshold voltage of thelow-side transistor to be as low as that of the high-side transistor(which can be, for example, 0.5V), having a small difference between thetwo threshold voltages helps in preventing effects such as reverserecovery losses. In some implementations, because an adjustable V_(CC)can be used as the reference voltage for the low-side inverter 74, adevice designer is afforded additional flexibility of manipulating theV_(T) of the low-side transistor 42, such that the effective thresholdvoltage V_(Teff) is substantially same as, or at least comparable to thethreshold voltage of the high-side transistor 40. For example, for aV_(CC) of 1.8V, V_(T) can be designed to be around 2.3V (which is wellwithin design limits), such that V_(Teff) is about 0.5V.

FIG. 5 shows a flowchart 500 depicting an example sequence of operationsfor adjusting a DC voltage source of a regulator in accordance with theoutput current. Operations include measuring an output current of aswitching transistor (510). The switching regulator can be substantiallysimilar to any of the regulators, 10, 100, 200, and 400 described abovewith reference to FIGS. 1, 2, 3, and 4, respectively. The switchingtransistor can include a high-side transistor and a low side-transistorwherein the high-side transistor and the low-side transistor are drivenusing a first gate voltage and a second, different gate voltage,respectively.

Operations also include adjusting a DC voltage source of the switchingregulator such that the first gate voltage is adjusted in accordancewith the measured output current. As the output current increases, theDC voltage source can be adjusted to increase the first gate voltage.This can ensure that the saturation current through the high-sidetransistor remains substantially constant for different values of theoutput current and the potential at the drain of the high-sidetransistor does not drop significantly. Measurement of the outputcurrent can be done using, for example, a current sensor. The currentsensor can be part of a feedback circuit such as the feedback circuit 50described with reference to FIG. 1.

In some implementations, the feedback circuit can facilitate adjustingthe DC voltage source, for example, by providing a suitable controlsignal to a controller of the adjustable DC voltage source. The feedbackcircuit can include a computing device that includes a processor, memoryand storage device, for generating the control signal based on themeasured output current. The DC voltage source can be adjusted as amonotonic function of the output current. For example, the output of theDC voltage source can be linearly increased within a range for a rangeof output current values. For example, for zero output current, theoutput of the DC voltage source can be between 1.7V and 1.8V, and for a30 A output current, the output of the DC voltage source can be adjustedto about 2V. The output can vary is a linear, quadratic, or higher ordermonotonic fashion between, for example, 1.7V and 2V.

A number of implementations have been described. Nevertheless, it willbe understood that various modifications can be made without departingfrom the spirit and scope of the disclosure. Certain implementations caninclude combinations of features from the various implementationsdescribed above. For example, a kickback protection circuit can be usedin conjunction with a feedback circuit for adjusting the VCC inaccordance with the output current. Other embodiments are within thescope of the following claims.

What is claimed is:
 1. A method comprising: driving a gate of ahigh-side transistor of a switching regulator using a high-side drivercircuit, the high-side driver circuit including a positive voltageterminal electrically coupled to a first power rail; driving a gate of alow-side transistor of the switching regulator using a low-side drivercircuit, the low-side driver circuit including a positive voltageterminal electrically coupled to a second power rail; powering thesecond power rail via a voltage source electrically coupled to thesecond power rail, irrespective of whether a transistor electricallycoupled between the second power rail and the first power rail isoperating in a conductive state; measuring an output current passingthrough an output terminal of the switching regulator; and in responseto an increase in the measured output current: adjusting the voltagesource to increase a voltage of the second power rail, and switching onthe transistor electrically coupled between the second power rail andthe first power rail to drive the first power rail from the voltagesource.
 2. The method of claim 1, further comprising controlling thevoltage source such that the voltage of the second power rail is between1.5V and 1.8V when the measured output current is substantially zero. 3.The method of claim 1, further comprising controlling the voltage sourcesuch that the voltage of the second power rail is at least 2V when themeasured output current is 30 A.
 4. The method of claim 1, furthercomprising controlling the voltage source such that the voltage of thesecond power rail is a monotonic function of the measured output currentfor a range of output current values.
 5. The method of claim 1, furthercomprising controlling the voltage source such that a saturation currentof the high-side transistor is substantially constant for a range ofoutput current values.
 6. A switching regulator having an input terminaland an output terminal, the switching regulator comprising: a high-sidetransistor between the input terminal and an intermediate terminal; alow-side transistor between the intermediate terminal and ground; ahigh-side driver circuit for driving a gate of the high-side transistor,the high-side driver circuit including a positive voltage terminalelectrically coupled to a first power rail; a low-side driver circuitfor driving a gate of the low-side transistor, the low-side drivercircuit including a positive voltage terminal electrically coupled to asecond power rail; a third transistor electrically coupled between thefirst and second power rails; a direct current (DC) voltage sourceelectrically coupled to the second power rail to power the second powerrail irrespective of whether the third transistor is operatingconductive state; and a controller that controls the high-side drivercircuit and the low-side driver circuit to respectively drive thehigh-side and low-side transistors to alternately couple theintermediate terminal to the input terminal and ground, wherein thecontroller is configured to (a) increase an output voltage of the DCvoltage source and (b) switch on the third transistor, in response to anincrease in an output current passing through an output terminal of theswitching regulator to drive the first power rail from the DC voltagesource.
 7. The switching regulator of claim 6, wherein the high-sidedriver circuit includes an inverter with an input terminal and an outputterminal.
 8. The switching regulator of claim 7, wherein the inputterminal is connected to the controller and the output terminal isconnected to the gate of the high-side transistor.
 9. The switchingregulator of claim 6, wherein the controller is configured to receive asignal indicative of a measurement of the output current.
 10. Theswitching regulator of claim 6, wherein the controller is configured toadjust the DC voltage source such that the output voltage of the DCvoltage source is between 1.5V and 1.8V for substantially no outputcurrent.
 11. The switching regulator of claim 6, wherein the controlleris configured to adjust the DC voltage source such that the outputvoltage of the DC voltage source is at least 2V for an output currentsubstantially equal to 30 A.
 12. The switching regulator of claim 6,wherein the controller is configured to adjust the DC voltage sourcesuch that the output voltage of the DC voltage source is a monotonicfunction of the output current for a range of output current values. 13.The switching regulator of claim 6, wherein the controller is configuredto adjust the DC voltage source such that a saturation current of thehigh-side transistor is substantially constant for a range of outputcurrent values.
 14. The switching regulator of claim 6, furthercomprising a current sensor configured to measure the output current atthe output terminal of the switching regulator.
 15. A system forcontrolling a switching regulator, comprising: a high-side drivercircuit for driving a gate of a high-side transistor of the switchingregulator, the high-side driver circuit including a positive voltageterminal electrically coupled to a first power rail; a low-side drivercircuit for driving a gate of a low-side transistor of the switchingregulator, the low-side driver circuit including a positive voltageterminal electrically coupled to a second power rail; a transistorelectrically coupled between the first and second power rails; andcircuitry configured to (a) control a direct current (DC) voltage sourceelectrically coupled to the second power rail such that an outputvoltage of DC voltage source increases and (b) switch on the transistorelectrically coupled between the first and second power rails, inresponse to an increase in an output current passing through an outputterminal of the switching regulator, to drive the first power rail fromthe DC voltage source; the DC voltage source configured to power thesecond power rail irrespective of whether the transistor electricallycoupled between the first and second power rails is operating in aconductive state.
 16. The system of claim 15, wherein the circuitry isconfigured to control the DC voltage source such that the output voltageof the DC voltage source is between 1.5V and 1.8V when the outputcurrent is substantially zero.
 17. The system of claim 15, wherein thecircuitry is configured to control the DC voltage source such that theoutput voltage of the DC voltage source is at least 2V when the outputcurrent is substantially equal to 30 A.
 18. The system of claim 15,wherein the circuitry is configured to control the DC voltage sourcesuch that the output voltage of the DC voltage source is a monotonicfunction of the output current for a range of output current values.